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**New for January 2012!** Here's a new page on a three-dimensional Smith Chart!

We've got our own Smith chart tutorial here, thanks to a fan from Florida, Mike Weinstein, who really knows this subject, and is a fine writer too. If anyone else wants to be a technical contributor on their favorite microwave subject, please contact us.

If you want to download a Smith chart in pdf or gif format, we have several different ones in our download area!

The Smith chart was developed by Philip Smith at Bell Telephone's Radio Research Lab during the 1930s. Be sure to check out our entry on Philip Smith in our Microwave Hall of Fame! Phil's wife still operates Analog Instruments, the company that sells the chart. Their snail mail address is:

Analog Instruments Company,

P.O. Box 950,

New Providence, NJ 07974,

(908) 464-4214.

A clickable index to our growing Smith chart page:

Which way is up and where's that short circuit?

## What's a Smith chart?

What is a Smith chart? It's really just a **plot of complex reflection overlaid with an impedance and/or admittance grid**
referenced to a 1-ohm characteristic impedance. That's it! Transmission
coefficient, which equals unity plus reflection coefficient, may also
be plotted (see below). You can find books and articles describing how a
Smith chart is a graphical representation of the transmission line
equations and the mathematical reasons for the circles and arcs, but
these things don't really matter when you need to get the job done. What
matters is knowing the basics and how to use them, like always.

The Smith chart contains almost all possible impedances, real or imaginary, within one circle. All imaginary impedances from - infinity to + infinity are represented, but only positive real impedances appear on the "classic" Smith chart. Yes, it is possible to go outside the Smith chart "unity" circle, but only with an active device because this implies negative resistance.

One thing you give up when plotting reflection coefficients on a Smith chart is a direct reading of a frequency axis. Typically, plots that are done over any frequency band have markers calling out specific frequencies.

Why use a Smith chart? It's got all those funny circles and arcs, and good ol' rectangular plots are much better for displaying things like VSWR, transmission loss, and phase, right? Perhaps sometimes a rectangular plot is better, but a Smith chart is the RF engineer's best friend! It's easy to master, and it adds an air of "analog coolness" to presentations, which will impress your friends, if not your dates! A master in the art of Smith-charting can look at a thoroughly messed up VSWR of a component or network, and synthesize two or three simple networks that will impedance-match the circuit in his head!

## Impedance and admittance

A quick refresher on the basic quantities that have units of ohms or its reciprocal, Siemens (sometimes called by its former name, mhos), is helpful since many of them will be referenced below. We all think of resistance (R) as the most fundamental of these quantities, a measure of the opposition to current flow that causes a potential drop, or voltage, according to Ohms Law: V=I*R. By extension, impedance (Z) is the steady state AC term for the combined effect of both resistance and reactance (X), where Z=R+jX. (X=jwL for an inductor, and X=1/jwC for a capacitor, where w is the radian frequency or 2*pi*f.) Generally, Z is a complex quantity having a real part (resistance) and an imaginary part (reactance).

We often think in terms of impedance and its constituent quantities of resistance and reactance. These three terms represent "opposition" quantities and are a natural fit for series-connected circuits where impedances add together. However, many circuits have elements connected in parallel or "shunt" that are a natural fit for the "acceptance" quantity of admittance (Y) and its constituent quantities of conductance (G) and susceptance (B), where Y=G+jB. (B=jwC for a capacitor, and B=1/jwL for an inductor.) Admittances add together for shunt-connected circuits. Remember that Y=1/Z=1/(R+jX), so that G=1/R only if X=0, and B=-1/X only if R=0.

When working with a series-connected circuit or inserting elements in
series with an existing circuit or transmission line, the resistance
and reactance components are easily manipulated on the **"impedance"**
Smith chart. Similarly, when working with a parallel-connected circuit
or inserting elements in parallel with an existing circuit or
transmission line, the conductance and susceptance components are easily
manipulated on the **"admittance"** Smith chart. The **"immittance"** Smith chart simply has both the impedance and admittance grids on the same chart, which is useful for cascading series-connected with parallel-connected circuits.

## Which way is up and where's that short circuit?

The most common orientation of the Smith chart places the resistance axis horizontally with the short circuit (SC) location at the far left. There's a good reason for this: the voltage of the reflected wave at a short circuit must cancel the voltage of the incident wave so that zero potential exists across the short circuit. In other words, the voltage reflection coefficient must be -1 or a magnitude of 1 at an angle of 180 degrees. Since angles are measured from the positive real axis and the real axis is horizontal, the short circuit location and horizontal orientation make sense. ("Voltage" is underlined above because the current reflection coefficient of a short circuit being +1 would place the short circuit location at the right end, but let's not go there.)

For an open circuit (OC), the reflected voltage is equal to and in phase with the incident voltage (reflection coefficient of +1) so that the open circuit location is on the right. In general, the reflection coefficient has a magnitude other than unity and is complex. For reasons we won't bore you with here, anywhere above the real axis is inductive (L) and anywhere below is capacitive (C).

## "Yes sir!" and please don't flip me!

Can't remember which way to rotate the locus when moving along the
transmission line? Well, it's clockwise toward the generator
because **generals make you go like clockwork**. Also keep
in mind that moving "x" degrees along the line moves a point on the
locus "2x" degrees on the chart because the reflected wave must
transverse the round-trip distance moved (remember, it's the reflection
coefficient). Alternately, you could remember that the impedance
repeats itself every half wavelength along a uniform transmission line,
so you must move one time around the chart to wind up at the same
impedance. Of course, a physical line length has variable electrical
length over a frequency band, so a fixed impedance will spread out to a
locus when viewed through a connected transmission line. This is why it
is always easier to obtain a wideband match when you're close to the
device or discontinuity.

Many older RF engineers advocate reflecting through the origin to "convert" from impedance to admittance and vice versa. That's why you see the same axis labeled "INDUCTIVE REACTANCE OR CAPACITIVE SUSCEPTANCE" on the original Smith chart, for example. This can be confusing, you've got to do the flip, you need to remember what the grid currently represents, and SC, OC, L & C are moving targets! Why not just keep the reflection coefficient where it belongs and use the appropriate grid? We have computers, color printers, and immittance charts these days. (If you still like to do things manually and either can't deal with all those lines on an immittance chart or are color blind, use a transparency overlay and a blank piece of paper.)

## Normalization

Moving along a uniform transmission line doesn't change the magnitude
of the reflection coefficient or its radial distance plotted on the
Smith chart. But what about when the impedance of the line changes, for
example, when a quarter-wavelength transformer is used? Reflection coefficient (Gamma) is, by definition, normalized to the characteristic impedance (Z_{0}) of the transmission line:

Gamma = (Z_{L}-Z_{0}) / (Z_{L}+Z_{0})

where Z_{L} is the load impedance or the impedance at the
reference plane. Note that Gamma is generally complex. Likewise, the
impedance (admittance) values indicated on the grid lines are normalized
to the characteristic impedance (admittance) of the transmission line
to which the reflection coefficient is normalized.

When Z_{0} changes just past the junction between two
different transmission lines, so does the reflection coefficient.
Determining the new impedance (admittance) is simple: **multiply by the characteristic impedance (admittance) of the current line** (this yields the unnormalized value), **then divide by the characteristic impedance (admittance) of the new line** to obtain the new renormalized value.

The new Gamma may be calculated with the formula above or graphically determined by drawing a line from the origin to the new renormalized value. This example ignores the effect of the step discontinuity encountered in physical (non-ideal) transmission lines, which typically introduces some shunt capacitance.

## How much is that stub worth?

Transmission line stubs are essential for impedance matching, introducing small amounts of phase delay (in pairs to cancel reflections), biasing, etc. Are you sometimes unsure that a short-circuited stub that's less than a quarter wavelength is inductive, or whether a wide, low impedance stub in shunt with the main line has low or high Q? A smith chart can tell you these things and give you hard numbers in a jiffy.

For example, a short-circuited stub is just a short circuit seen through a length of transmission line. Place your pencil at the SC point on the chart and move clockwise toward the generator (at the other end of the stub) on the rim by an amount less than a quarter wavelength (180 degrees on the chart). This is in the inductive region; moving more than 180 degrees makes the stub input look capacitive. At exactly one-quarter wavelength, the impedance is infinite, an open circuit. You can do the same for an open-circuited stub by starting at the OC point on the chart.

The real power of the Smith chart comes into play for analysis over a
frequency band. Suppose you want to know the susceptance variation of a
50-ohm short-circuited stub over a 3:1 band. This stub could be placed
in shunt with the main line at the proper point to double-tune a
series-resonant locus, for instance. (We'll cover double-tuning, a very
powerful technique, in a future update.) Shown in the admittance chart
below is a short-circuited stub that's one-eight wavelength long at the
low end and thus is three-eighths wavelengths long at the high end of
the 3:1 frequency band. The normalized susceptance varies from -1.0 siemens (inductive) at f_{low} to zero (open circuit) at midband to +1.0 siemens (capacitive) at f_{high}. Therefore, the unnormalized susceptance varies between Â±1.0*Y_{0} siemens, where Y_{0} (=1/Z_{0}) is the characteristic admittance of the stub. When the characteristic admittance (Y_{0})
of the stub is the same as the main line, the normalized susceptance of
the stub may be added to the normalized admittance of the load at each
frequency to yield the normalized admittance of the parallel
combination. When Y_{0} of the stub differs from that of the main line, renormalize the stub's susceptance by Y_{0} of the main line before adding.

Generally, the desired susceptance variation is other than Â±0.02 siemens (Â±1.0*Y_{0}), which a 50-ohm stub would provide in this example. Suppose a 50-ohm main line locus needs a normalized
susceptance variation of only Â±0.4 siemens instead of Â±1.0 siemens.
Achieve this simply by making the characteristic admittance of the stub
equal to 0.4 times that of the main line or Y_{0}=0.4*0.02=0.008
siemens. The stub is now a 125-ohm line (50/0.4) and its susceptance
varies less over the band, so it has lower Q. Note that the unnormalized
values are rarely needed, normalized values may be renormalized by the
ratio of the characteristic impedances involved.

Next, consider a stub for changing the transmission phase of a
main-line signal. We know that an open-circuited stub less than a
quarter wavelength long retards the phase (adds phase delay), and this
is readily seen on the Smith chart: Moving clockwise from the OC
position, an open-circuited stub has a transmission coefficient (1 +
Gamma) with a negative phase angle. Similarly, a short-circuited stub
less than a quarter wavelength long will advance the phase. The
following figure illustrates the phase delay of 50-ohm and 25-ohm
open-circuited stubs in shunt with a 50-ohm main line. Note that the
result is mismatched, which is why stubs should be added in pairs to cancel reflections. Also note that the amount of phase delay increases as the characteristic impedance of the stub decreases (a larger Y_{0} produces a larger unnormalized susceptance), which makes sense since a wider stub looks like a larger capacitor.

## Single-stub matching

The ability to obtain a reasonable match over a frequency band
depends upon the magnitude of the mismatch, the desired bandwidth, and
the complexity of matching circuit. But at any one frequency any
impedance mismatch can be perfectly matched to the characteristic
impedance of the transmission line, as long as it's not on the rim of
the chart (perfect reflection, |Gamma| = 1). And this always can be done
with one stub that's less than a quarter-wavelength long. The technique
is simple: **move along the transmission line to rotate the
mismatch to the unity resistance (conductance) circle and insert the
appropriate type and length of stub in series (shunt) with the main line
to move along this circle to the origin**. If the far end of the
stub is either a short or open circuit (or generally, any pure
reactance), its input end is also a pure reactance (susceptance) so that
it doesn't affect the resistance (conductance) component of the
mainline impedance (admittance).

Since it's usually easier to add a stub in parallel with a
transmission line, the example shown below uses an admittance chart
because, at the attachment point, the resulting admittance is the sum of
the stub's input susceptance and the main line admittance. First, the
mismatched point is rotated around the origin until it reaches the unity
conductance circle. Then, the characteristic impedance and length of
the stub is chosen such that its input susceptance is equal and opposite
to the main line susceptance indicated on the unity conductance circle.
The example shows two cases: move toward the generator 39 degrees of
line and add a short-circuited stub that provides 0.8 siemens normalized
**inductive** susceptance, or move toward the generator
107 degrees of line and add an open-circuited stub that provides 0.8
siemens normalized **capacitive** susceptance.

There are an infinite number of possible solutions because, at one frequency, a stub of any characteristic impedance can provide the necessary normalized susceptance simply by adjusting its length. The differences show up when looking over a frequency band. For example, the stub's length may be increased by an integer multiple of half-wavelengths at a particular frequency and its input susceptance at this frequency will not change. But over a frequency band, the susceptance will vary considerably more than if the extra length had not been added.

## Some Smith chart links

Here are some links on Smith charts for anyone that wants additional info or needs a Smith chart clock!

http://www.sss-mag.com/smith.html

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